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850kHz 700mA Synchronous Buck DC/DC Converter General Description
The AAT1151 SwitchRegTM is a member of Analogic TechTM's Total Power ManagementTM IC product family. The step-down switching converter is ideal for applications where high efficiency is required over the full range of the output load conditions. The 2.7 to 5.5V input voltage range makes the AAT1151 ideal for single-cell Lithium Ion/ Polymer battery applications. Capable of more than 700mA with internal MOSFETs, the currentmode controlled IC provides high efficiency using synchronous rectification. Fully integrated compensation simplifies system design and lowers external part count. The device operates at a fixed 850kHz switching frequency and enters PFM mode for light load current to maintain high efficiency across all load conditions. The AAT1151 is available in MSOP-8 and 16 pin 3x3mm QFN package rated over -40 to 85C.
AAT1151
Features
* * * * * * * * * * * * * * * * *
SwitchRegTM
VIN Range 2.7-5.5 Volts Up to 95% Efficiency 110 m RDS(ON) Internal Switches < 1A Shutdown Current 850kHz Switching Frequency Fixed VOUT or Adjustable VOUT 1.0V Integrated Power Switches Synchronous Rectification Current Mode Operation Internal Compensation Stable with Ceramic Capacitors PWM and PFM for optimum efficiency for all load conditions Internal Soft Start Over-Temperature Protection Current Limit Protection MSOP-8 and 16 pin QFN 3x3mm Package -40 to +85C Temperature Range
Preliminary Information
Applications
* * * * * * * Wireless Notebook Adapters Notebook Computers Digital Cameras Cellular Phones MP3 Players PDAs USB Powered Equipment
Typical Application
INPUT
10F
VP FB
AAT1151
LX ENABLE 100 VCC
3.0H
OUTPUT SGND 0.1F PGND 47F
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850kHz 700mA Synchronous Buck DC/DC Converter Pin Descriptions
Pin #
MSOP-8 QFN33-16
AAT1151
Symbol
FB
Function
Feedback input pin. This pin is connected to the converter output. It is used to set the output of the converter to regulate to the desired value via an internal resistive divider. For an adjustable output an external resistive divider is connected to this pin on the 1V model. Signal Ground. Connect the return of all small signal components to this pin. (see board layout rules) Enable input pin. A logic high enables the converter, a logic low forces the AAT1151 into shutdown mode reducing the supply current to less than 1A. The pin should not be left floating. Bias supply. Supplies power for the internal circuitry. Connect to input power via low pass filter with decoupling to SGND. Input Supply Voltage for the converter power stage. Must be closely decoupled to PGND. Connect inductor to these pins. Switching node internally connected to the drain of both high and low-side MOSFETs. Main power ground return pin. Connect to the output and input capacitor return. (see board layout rules) Not internally connected.
1
4
2 3
5, 6 7
SGND EN
4 5 6, 7 8
9 10, 11, 12 13, 14, 15 1, 2, 3 8, 16
VCC VP LX PGND n/c
Pin Configuration
MSOP-8 (Top view) QFN33-16 (Top view)
N/C LX LX LX
16 15 14 13 12 11 10 9 5 6 7 8
FB SGND EN VCC
1 2
8 7
3 4
6 5
PGND LX LX VP
1 2
PGnd PGnd PGnd FB
1 2 3 4
Vp Vp Vp VCC
AAT 1151
SGND
SGND
NC
EN
2
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850kHz 700mA Synchronous Buck DC/DC Converter Absolute Maximum Ratings1
Symbol
VCC, VP VLX VFB VEN TJ VESD
AAT1151
Description
VCC, VP to GND LX to GND FB to GND EN to GND Operating Junction Temperature Range ESD Rating 2 - HBM
Value
6 -0.3 to VP+0.3 -0.3 to VCC+0.3 -0.3 to 6 -40 to 150 3000
Units
V V V V C V
Notes: 1: Stresses above those listed in Absolute Maximum Ratings may cause permanent damage to the device. Functional operation at conditions other than the operating conditions specified is not implied. Only one Absolute Maximum rating should be applied at any one time. 2: Human body model is a 100pF capacitor discharged through a 1.5K resistor into each pin.
Thermal Characteristics
Symbol
JA PD JA PD
Description
Thermal Resistance (MSOP-8) 2 Maximum Power Dissipation (MSOP-8) (TA = 25C) 2, 3 Thermal Resistance (QFN33-16) 2 Maximum Power Dissipation (QFN33-16) (TA = 25C) 2, 4
Value
150 667 50 2.0
Units
C/W mW C/W W
Note 2: Mounted on a demo board. Note 3: Derate 6.7mW/C above 25C. Note 4: Derate 20mW/C above 25C.
Recommended Operating Conditions
Symbol
T
Description
Ambient Temperature Range
Value
-40 to 85
Units
C
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850kHz 700mA Synchronous Buck DC/DC Converter Electrical Characteristics1
(VIN = VCC = VP = 5V, TA = -40 to 85C unless otherwise noted. Typical values are at TA = 25C) Symbol
VIN VOUT VUVLO VUVLO(HYS) IIL IIH IQ ISHDN ILIM RDS(ON)L RDS(ON)H VOUT (VOUT*VIN) VOUT/VOUT FOSC VEN(L) VEN(H) TSD THYS
AAT1151
Description
Input Voltage Range Output Voltage Tolerance Under Voltage Lockout Under Voltage Lockout Hysteresis Input Low Current Input High Current Quiescent Supply Current Shutdown Current Current Limit High Side Switch On Resistance Low Side Switch On Resistance Efficiency Load Regulation Line Regulation Oscillator Frequency Enable Threshold Low Enable Threshold High Over Temp Shutdown Threshold Over Temp Shutdown Hysteresis
Conditions
VIN = VOUT + 0.2 to 5.5V, IOUT = 0 to 700 mA VIN Rising VIN Falling
Min
2.7 -3.0
Typ
Max
5.5 +3.0 2.5
Units
V % V V mV A A A A A m m % % %/V KHz V V C C
1.2 250 1.0 1.0 300 1.0 150 150
VIN = VFB = 5.5V VIN = VFB= 0 V No Load, VFB= 0 V VEN = 0 V, VIN= 5.5V TA = 25C 1.2 TA = 25C TA = 25C IOUT = 300mA, VIN= 3.5 V VIN= 4.2V, ILOAD = 0 - 700mA VIN= 2.7 to 5.5V TA = 25C 600 1.4
160
110 100 92 0.9 0.1 850
1200 0.6
140 15
Note 1: The AAT1151 is guaranteed to meet performance specification over the -40 to 85C operating range and are assured by design, characterization and correlation with statistical process controls.
4
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850kHz 700mA Synchronous Buck DC/DC Converter Typical Characteristics
Output Ripple 1.8V 50mA VIN = 3.6V Circuit of Figure 1
20 1.4
AAT1151
Soft Start 1.8V 0.7A VIN = 3.6V Circuit of Figure 1
4 3.5 3 3 2 1 0 -1 -2 -3 -4
Output Voltage (AC coupled) (top) (mV)
Enable (top) Output (middle) (V)
10 0 -10 -20 -30 -40 -50 -60
1.2
Inductor Current (bottom) (A)
Inductor Current (bottom) (A)
1 0.8 0.6 0.4 0.2 0 -0.2
2.5 2 1.5 1 0.5 0 -0.5
Time (2s/div)
Time (200s/div)
Output Ripple 1.8V 0.7A VIN = 3.6V Circuit of Figure 1
20 3.5 3
Line Transient Response 1.8V 0.7A Circuit of Figure 1
4.4 4.2 120 100
Output Voltage (AC coupled) (top) (mV)
10 0 -10 -20 -30 -40 -50 -60
Inductor Current (bottom) (A)
Output Voltage (bottom) (mV)
2 1.5 1 0.5 0 -0.5
Input Voltage (top) (V)
2.5
4 3.8 3.6 3.4 3.2 3 2.8
80 60 40 20 0 -20 -40
Time (2s/div)
Time (20s/div)
Load Transient Response 50mA to 0.7A VIN = 3.6V - Circuit of Figure 1
Output Voltage (top) (mV) (AC coupled)
40 20 0 -20 -40 -60 -80 -100 -120 3.5 3
Line Transient Response 1.8V 50mA Circuit of Figure 1
4.4 4.2 120 100
Inductor Current (bottom) (A)
Output Voltage (bottom) (mV)
2 1.5 1 0.5 0 -0.5
Input Voltage (top) (V)
2.5
4 3.8 3.6 3.4 3.2 3 2.8
80 60 40 20 0 -20 -40
Time (200s/div)
Time (20s/div)
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850kHz 700mA Synchronous Buck DC/DC Converter Typical Characteristics
No Load Supply Current vs. Input Voltage
250 890
AAT1151
Frequency vs. Input Voltage
Supply Current (A)
Frequency (kHz)
200 150 100 50 0 2.5
T = 85C T = 25C T = -40C
880
870
860
850 3 3.5 4 4.5 5 5.5 2.5 3 3.5 4 4.5 5 5.5
Input Voltage (V)
Input Voltage (V)
Output Voltage vs. Temperature
3.0
1.794 1.792
Load and Line Regulation
2.0
VIN = 4.2V VIN = 3.6V VIN = 2.7V
Output Voltage (V)
VOUT Error (%)
-20 0 20 40 60 80 100
1.79 1.788 1.786 1.784 1.782 1.78 -40
1.0 0.0 -1.0 -2.0 -3.0 1 10 100
1000
Temperature (C)
Load Current (mA)
Switching Frequency vs. Temperature
1200
Output Ripple Circuit of Figure 1
20
1000
Frequency (kHz)
Ripple (mV)
800 600 400 200 0 -40 -20 0 20 40 60 80 100
15
VIN = 2.7V
10
VIN = 3.6V
5
VIN = 4.2V
0 1 10 100 1000
Temperature (C)
IOUT (mA)
6
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850kHz 700mA Synchronous Buck DC/DC Converter Functional Block Diagram
VCC VP= 2.7V- 5.5V
AAT1151
1.0V REF
FB
OP. AMP
CMP
DH
LOGIC
LX
1M
DL Temp. Sensing
OSC
SGND
EN
PGND
Operation
Control Loop
The AAT1151 is a peak current mode buck converter. The inner, wide bandwidth loop controls the peak current of the output inductor. The output inductor current is sensed through the P-Channel MOSFET (high side) and is also used for short circuit and overload protection. A fixed slope compensation signal is added to the sensed current to maintain stability. The loop appears as a voltage programmed current source in parallel with the output capacitor. The voltage error amplifier output programs the current loop for the necessary inductor current to force a constant output voltage for all load and line conditions. The voltage feedback resistive divider is internal, dividing the output voltage to the error amplifier reference voltage of 1.0V. The voltage error amplifier does not have a large DC gain typical of most error amplifiers. This eliminates the need for external compensation components while still providing sufficient DC loop gain for load regulation. The voltage loop crossover frequency and phase margin are set by the output capacitor value only.
PFM/PWM Operation
Light load efficiency is maintained by way of Pulse Frequency Modulation (PFM) control. The AAT1151 PFM control forces the peak inductor current to a minimum level regardless of load demand. At medium to high load demand this has no effect on circuit operation and normal PWM controls take over. PFM reduces the switching frequency at light loads thus reducing the associated switching losses.
Soft-Start/Enable
Soft start increases the inductor current limit point in discrete steps when the input voltage or enable input is applied. It limits the current surge seen at the input and eliminates output voltage overshoot. The enable input, when pulled low, forces the AAT1151 into a low power non-switching state. The total input current during shutdown is less that 1A.
Power and Signal Source
Separate small signal ground and power supply pins isolate the internal control circuitry from the noise associated with the output MOSFET switching. The low pass filter R1 and C3 in schematic figures 3 and 4 filters the noise associated with the power switching. 7
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850kHz 700mA Synchronous Buck DC/DC Converter
Current Limit and Over-temperature Protection
For overload conditions the peak input current is limited. Figure 1 displays the VI current limit characteristics. As load impedance decreases and the output voltage falls closer to zero, more power is dissipated internally, raising the device temperature. Thermal protection completely disables switching when internal dissipation becomes excessive, protecting the device from damage. The junction over-temperature threshold is 140C with 10C of hysteresis.
AAT1151
dard value of 3.0H gives 38% ripple current. A 3.0H inductor selected from the Sumida CDRH5D28 series has a 24 m DCR and a 2.4 DC current rating. At full load the inductor DC loss is 24mW which amounts to a 1.6% loss in efficiency.
Input Capacitor
The primary function of the input capacitor is to provide a low impedance loop for the edges of pulsed current drawn by the AAT1151. A low ESR/ESL ceramic capacitor is ideal for this function. To minimize the stray inductance the capacitor should be placed as close as possible to the IC. This keeps the high frequency content of the input current localized; minimizing radiated and conducted EMI while facilitating optimum performance of the AAT1151. Ceramic X5R or X7R capacitors are ideal for this function. The size required will vary depending on the load, output voltage and input voltage source impedance characteristics. A Typical value is around 10F. The input capacitor RMS current varies with the input voltage and the output voltage. The equation for the maximum RMS current in the input capacitor is: VO V * 1- O VIN VIN
Inductor
The output inductor is selected to limit the ripple current to some predetermined value, typically 20-40% of the full load current at the maximum input voltage. Manufacturer's specifications list both the inductor DC current rating, which is a thermal limitation, and the peak current rating, which is determined by the saturation characteristics. The inductor should not show any appreciable saturation under all normal load conditions. During over load and transient conditions, the average current in the inductor can meet or exceed the current limit point of the AAT1151. These conditions can tolerate greater saturation in the inductor without degradation in converter performance. Some inductors may meet the peak and average current ratings yet result in excessive losses due to a high DCR. Always consider the losses associated with the DCR and its effect on the total converter efficiency when selecting an inductor. For a 1.0 Amp load and the ripple set to 40% at the maximum input voltage, the maximum peak to peak ripple current is 280mA. The inductance value required is 2.84H.
VOUT VOUT L= I *k*F * 1- V O IN = 1.5V * 1 - 1.5V 1A * 0.4 * 850kHz 4.2V
IRMS = IO *
The input capacitor RMS ripple current reaches a maximum when VIN is two times the output voltage where it is approximately one half of the load current. Losses associated with the input ceramic capacitor are typically minimal and not an issue. The proper placement of the input capacitor can be seen in the reference design layout in figure 3.
Output Capacitor
Since there are no external compensation components, the output capacitor has a strong effect on loop stability. Lager output capacitance will reduce the crossover frequency with greater phase margin. For the 1.5V 1A design using the 4.1H inductor, a 47F capacitor provides a stable loop but with only 35 degrees of phase margin at a crossover frequency of 100 kHz. Doubling the capacitance to 100F reduces the crossover frequency to half while increasing the phase margin to 60 degrees. In addition to assisting stability, the output capacitor limits the output ripple
= 2.84H The factor "k" is the fraction of full load selected for the ripple current at the maximum input voltage. For ripple current at 40% of the full load current the peak current at will be 120% of full load. Selecting a stan8
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850kHz 700mA Synchronous Buck DC/DC Converter
and provides holdup during large load transitions. A 100uF X5R or X7R ceramic capacitor provides sufficient bulk capacitance to stabilize the output during large load transitions and has ESR and ESL characteristics necessary for low output ripple. The output capacitor rms ripple current is given by
1 2* 3 ( VOUT+ VFWD) * (VIN - VOUT) L * F * VIN
AAT1151
Layout
Figures 2 and 3 display the suggested PCB layout for the AAT1151. The following guidelines should be used to help insure a proper layout. * * * The input capacitor (C1) should connect as closely as possible to VPOWER (pin 5) and PGND (pin 8). C2, and L1, should be connected as closely as possible. The connection L1 to the LX node should be as short as possible. The feedback trace (pin 1) should be separate from any power trace and connect as closely as possible to the load point. Sensing along a high current load trace will degrade DC load regulation. The resistance of the trace from the load return to the PGND (pin 8) should be kept to a minimum. This will help to minimize any error in DC regulation due to differences in the potential of the internal signal ground and the power gnd. Low pass filter R1 and C3 provide a cleaner bias source for the AAT1151 active circuitry. C3 should be placed as close as possible to SGND (pin 2) and VCC (pin 4).
IRMS =
*
For a ceramic capacitor the ESR is so low that dissipation due to the rms current of the capacitor is not a concern. Tantalum capacitors with sufficiently low ESR to meet output voltage ripple requirements also have an RMS current rating well beyond that actually seen in this application.
*
*
2.7V-4.2V R1 100 R2 100k C2 0.1F R6 100k
U1 AAT1151-QFN 12 11 10 9 7 6 16 5 Vp Vp Vp Vcc EN gnd n/c gnd Out LX LX LX n/c Pgnd Pgnd Pgnd 4 15 14 13 8 3 2 1 L1 3.3H C3-C7 4x10F
1.8V
C1 10F
C1 Murata 10uF 6.3V X5R GRM42-6X5R106K6.3 C2-C5 MuRata 10uF 6.3V GRM21BR60J106KE01L L1 Sumida CDRH3D16-4R7NC or CDRH3D16-3R3NC
Efficiency vs. Load Current VOUT = 1.8V
100
90
2.7V
Efficiency (%)
80
3.6V
4.2V
70
60
50 1 10 100 1000
Load Current (mA)
Figure 1. 9
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850kHz 700mA Synchronous Buck DC/DC Converter
AAT1151
Figure 2: MSOP Evaluation Board Top Layer
Figure 3: MSOP Evaluation Board Bottom Layer
Figure 4: QFN Evaluation Board Top Side
Figure 5: QFN Evaluation Board Bottom Side
Thermal Calculations
There are two types of losses associated with the AAT1151 output switching MOSFET, switching losses and conduction losses. The conduction losses are associated with the RDS(ON) characteristics of the output switching device. At the full load condition, assuming continuous conduction mode (CCM), a simplified form of the total losses is given by
Once the total losses have been determined the junction temperature can be derived from the JA for the MSOP-8 package.
TJ = P * JA + TAMB
Adjustable Output
For applications requiring an output other than the fixed available, the 1V version can be programmed externally. Resistors R3 and R4 of figure 5 force the output to regulate higher than 1 Volt. R4 should be 100 times less than the 1M internal resistance of the FB pin (recommended 10k). Once R4 is selected R3 can be calculated. For a 1.25 Volt output with R4 set to 10.0k, R3 is 2.55k.
P=
IO2 * (RDSON(HS) * VO + RDSON(LS) * (VIN * VO)) VIN
+ (t SW * F * I O * VIN + IQ) * VIN
where Iq is the AAT1151 quiescent current.
R3 = (VO - 1) * R4 = 0.25 * 10k = 2.55k
10
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850kHz 700mA Synchronous Buck DC/DC Converter
45 40 35 30
AAT1151
R4=10k
R3 (k)
25 20 15 10 5 0 1 1.5 2 2.5 3 3.5 4 4.5 5 5.5
Output Voltage (V)
Figure 6: R3 vs. VOUT for Adjustable Output using the AAT1151-1.0V
Vo+ 1.25V 0.7A R3 2.55k 1%
2.7V-5.5V 5 R1 100 R2 100k C1 10F C3 0.1 F 4 3 2
AAT1151-1.0 Vp Vcc EN FB LX LX 1 7 6 8
L1 3.3H R4 10k 1%
C2 47F
gnd Pgnd
VC1 Murata 10F 6.3V X5R GRM42-6X5R106K6.3 C2 MuRata 100F 6.3V GRM43-2 X5R 476M 47F 6.3V L1 Sumida CDRH3D16-3R3 NC
Figure 7: Adjustable Output Schematic
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850kHz 700mA Synchronous Buck DC/DC Converter
Design Example
Specifications IOUT 0.7A IRIPPLE 40% of full load at max VIN VOUT 1.5V VIN 2.7-4.2 V (3.6V nominal) FS 850 kHz TAMB = 85C
AAT1151
Maximum input capacitor ripple:
IRMS = I O * V V O * 1 - O = 0.35Arms VIN VIN
P = esr * IRMS2 = 5m * 0.352 A = 0.6mW
Inductor Selection:
L=
V VOUT 1.5V 1.5V 1 - OUT = 1= 4.05H IO k F VIN 0.7A 0.4 850kHz 4.2V
Select Sumida inductor CDRH3D16 3.3H 63m 1.8 mm height.
I =
1.5V VO V 1.5V 1- O = 1= 340mA L F VIN 3.3H 850kHz 4.2V
IPK = IOUT +
I = 0.7A + 0.17A = 0.87A 2
P = IO2 DCR = (0.7)2 63mW = 31mW
Output Capacitor Ripple Current:
IRMS = VOUT * (VIN - VOUT) 1 1.5V * (4.2V - 1.5V) * = 99mArms = L * F * VIN 2 * 3 3.3H * 850kHz * 4.2V 2* 3 1 *
Pesr = esr * IRMS2 = 5m * 992 mA = 50W
12
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850kHz 700mA Synchronous Buck DC/DC Converter
AAT1151 dissipation:
PTOTAL = IO2 * (RDSON(H) * VO + RDSON(L) * (VIN -VO)) VIN + (tsw * F * IO + IQ) * VIN
AAT1151
=
(0.72) * (0.2 * 1.5V + 0.187 * (4.2V - 1.5V))
4.2V
+ (20nsec * 850kHz * 0.7A + 0.3mA) * 4.2V = 0.145W
TJ(MAX) = TAMB + JA * PLOSS = 85C + 150C/W * 0.145W = 107C (MSOP-8)
= 85C + 50C/W * 0.145W = 92C (QFN33-16)
Surface Mount Inductors
Manufacturer
TaiyoYuden Toko Sumida Sumida Sumida MuRata MuRata MuRata
Part Number
NPO5DB4R7M A914BYW-3R5M-D52LC CDRH5D28-3R0 CDRH5D28-4R2 CDRH5D18-4R1 LQH55DN4R7M03 LQH66SN4R7M03 CDRH3D16-3R3
Value
4.7H 3.5H 3.0H 4.2H 4.1H 4.7H 4.7H 3.3H
Max DC Current
1.4A 1.34A 2.4A 2.2A 1.95A 2.7A 2.2A 1.1A
DCR ()
.038 .073 .024 .031 .057 .041 .025 .063
Size (mm) LxWxH
5.9x6.1x2.8 5.0x5.0x2.0 5.7x5.7x3.0 5.7x5.7x3.0 5.7x5.7x2.0 5.0x5.0x4.7 6.3x6.3x4.7 3.8x3.8x1.8
Type
Shielded Shielded Shielded Shielded Shielded Non-Shielded Shielded Shielded
Surface Mount Capacitors
Manufacturer
TDK MuRata MuRata MuRata MuRata
Part Number
C4532X5ROJ107M GRM43-2 X5R 107M 6.3 GRM43-2 X5R 476K 6.3 GRM40 X5R 106K 6.3 GRM42-6 X5R 106K 6.3
Value
100F 100F 47F 10F 10F
Voltage
6.3V 6.3V 6.3V 6.3V 6.3V
Temp. Co.
X5R X5R X5R X5R X5R
Case
1812 1812 1812 0805 1206
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850kHz 700mA Synchronous Buck DC/DC Converter Ordering Information
Output Voltage1 1.0V (Adj VOUT 1.0V) 1.0V (Adj VOUT 1.0V) 1.8V 2.5V Package MSOP-8 QFN33-16 MSOP-8 MSOP-8 Marking2 JHXYY JHXYY JIXYY JJXYY Part Number (Tape and Reel) AAT1151IKS-1.0-T1 AAT1151IVN-1.0-T1 AAT1151IKS-1.8-T1 AAT1151IKS-2.5-T1
AAT1151
Notes 1. Contact local sales office for custom options. 2. XYY = assembly and date code.
Package Information
MSOP-8
4 4 1.95 BSC
3.00 0.10
4.90 0.10
0.60 0.20 PIN 1 0.254 BSC 0.95 REF
3.00 0.10 10 5 0.95 0.15 0.85 0.10
0.075 0.075 0.65 BSC 0.30 0.08
All dimensions in millimeters.
14
GAUGE PLANE
0.155 0.075
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850kHz 700mA Synchronous Buck DC/DC Converter
QFN33-16
0.230 0.050 0.500 0.050
13
AAT1151
Pin 1 Dot By Marking
SLP 16L (3 x 3mm)
9 5
3.000 BSC
1.500 REF
Top View
Bottom View
0.000 0.050
0.203 0.0254
Side View
All dimensions in millimeters.
0.900
1.550 0.150 exposed pad
1
3.000 BSC
0.400 0.050
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850kHz 700mA Synchronous Buck DC/DC Converter
AAT1151
AnalogicTech cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in an AnalogicTech product. No circuit patent licenses, copyrights, mask work rights, or other intellectual property rights are implied. AnalogicTech reserves the right to make changes to their products or specifications or to discontinue any product or service without notice, and advise customers to obtain the latest version of relevant information to verify, before placing orders, that information being relied on is current and complete. All products are sold subject to the terms and conditions of sale supplied at the time of order acknowledgement, including those pertaining to warranty, patent infringement, and limitation of liability. AnalogicTech warrants performance of its semiconductor products to the specifications applicable at the time of sale in accordance with AnalogicTech's standard warranty. Testing and other quality control techniques are utilized to the extent AnalogicTech deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily performed.
Advanced Analogic Technologies, Inc.
830 E. Arques Avenue, Sunnyvale, CA 94085 Phone (408) 737-4600 Fax (408) 737-4611 16
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